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參數(shù)資料
| 型號(hào)： | LT1952MPGN#PBF |
| 廠商： | LINEAR TECHNOLOGY CORP |
| 元件分類： | 穩(wěn)壓器 |
| 英文描述： | SWITCHING CONTROLLER, 560 kHz SWITCHING FREQ-MAX, PDSO16 |
| 封裝： | 0.150 INCH, LEAD FREE, PLASTIC, SSOP-16 |
| 文件頁數(shù)： | 13/28頁 |
| 文件大小： | 357K |
| 代理商： | LT1952MPGN#PBF |
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LT1952/LT1952-1
20
19521fe
For SD_VSEC = 1.32V, fOSC = 200kHz and RDELAY = 40k
This gives k = 1 and tDELAY = 40ns.
Re-arranging the above equation to solve for SS_MAXDC
= VSS(REG)
= [0.6 + (tDELAYfOSC)(SD_VSEC)]/(k0.522)
=[0.6+(40ns200kHz)(1.32V)]/(10.522)
= (0.608)(1.32)/0.522 = 1.537V
Step 3: Calculate t(VSS(REG)) – t(VSS(ACTIVE))
Recall the time for SS_MAXDC to charge to a given voltage
VSS is given by:
t = RCHARGECSS(–1)ln(1–VSS/SS_MAXDC(DC))
(Figure 11 gives the model for SS_MAXDC charging)
For RT = 35.7k, RB = 100k, RCHARGE = 26.3k
For CSS = 0.1F, this gives t(VSS(ACTIVE))
= t(VSS(0.8V)) = 2.63e41e–7(–1)ln(1–0.8/1.84)
= 2.63e–3(–1)ln(0.565)=1.5e–3 s
t(VSS(REG)) = t(VSS(1.537V))=26.3k0.1F–1
ln(1 – 1.66/1.84) = 2.63e–3(–1)ln(0.146)
= 5e–3 s
The rise time for the converter output
= t(VSS(REG)) – t(VSS(ACTIVE)) = (5 – 1.5)e–3 s
= 3.5e–3 s
Example (3) Time For Maximum Duty Cycle Clamp to
Reach Within X% of Target Value
A maximum duty cycle clamp of 72% was calculated
previously in the section ‘Programming Maximum
Duty Cycle Clamp’. The programmed value used for
SS_MAXDC(DC) was 1.84V.
ThetimeforSS_MAXDCtochargefromitsminimumvalue
VSS(MIN) to within X% of SS_MAXDC(DC) is given by:
t(SS_MAXDC charge time within X% of target)
=t[(1–(X/100)SS_MAXDC(DC)]–t(VSS(MIN))
For X = 2 and VSS(MIN)=0.45V,t(0.981.84)–
t(0.45) = t(1.803) – t(0.45)
From previous calculations, t(0.45) = 7.3e – 4 s.
Using previous values for RT, RB, and CSS,
APPLICATIONS INFORMATION
t(1.803) = 2.63e–41e–7(–1)ln(1–1.803/1.84)
= 2.63e–3(–1)ln(0.02)=1.03e–2 s
HencethetimeforSS_MAXDCtochargefromitsminimum
reset threshold of 0.45V to within 2% of its target value
is given by:
t(1.803) – t(0.45) =
1.03e–2 – 7.3e–4 = 9.57e–3
Forward Converter Applications
The following section covers applications where the
LT1952/LT1952-1 are used in conjunction with other LTC
parts to provide highly efficient power converters using
the single switch forward converter topology.
95% Efficient, 5V, Synchronous Forward Converter
ThecircuitinFigure14isbasedontheLT1952-1toprovide
the simplest forward power converter circuit—using only
one primary MOSFET. The SOUT pin of the LT1952-1
provides a synchronous control signal for the LTC1698
located on the secondary. The LTC1698 drives secondary
side synchronous rectifier MOSFETs to achieve high
efficiency. The LTC1698 also serves as an error amplifier
and optocoupler driver.
Efficiency and transient response are shown in Figures 12
and 13. Peak efficiencies of 95% and ultra-fast transient
response are superior to presently available power
modules. Integrated soft-start, overcurrent detection and
short-circuit hiccup mode provide low stress, reliable
protection. In addition, the circuit in Figure 14 is an all-
ceramic capacitor solution providing low output ripple
voltage and improved reliability. The LT1952-based
convertercanbeusedtoreplacepowermoduleconverters
at a much lower cost. The LT1952 solution benefits from
thermalconductionofthesystemboardresultinginhigher
efficienciesandlowerriseincomponenttemperatures.The
7mm height allows dense packaging and the circuit can
easily be adjusted to provide an output voltage from 1.23V
to 26V. Higher currents are achievable by simple scaling
of power components. The LT1952-1-based solution in
Figure 14 is a powerful topology for replacement of a wide
range of power modules.
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