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參數(shù)資料
| 型號： | IR3651SPBF |
| 廠商： | International Rectifier |
| 英文描述： | HIGH VOLTAGE SYNCHRONOUS PWM BUCK CONTROLLER |
| 中文描述： | 高壓同步PWM降壓控制器 |
| 文件頁數(shù)： | 16/19頁 |
| 文件大?。?/td> | 397K |
| 代理商： | IR3651SPBF |
IR3651SP
b
F
10/11/2006
To cancel one of the LC filter poles, place the
zero before the LC filter resonant frequency pole:
Using equations (15) and (16) to calculate C
4
.
One more capacitor is sometimes added in
parallel with C
4
and R
3
. This introduces one more
pole which is mainly used to suppress the
switching noise.
The additional pole is given by:
The pole sets to one half of switching frequency
which results in the capacitor C
POLE
:
For a general solution for unconditionally stability
for any type of output capacitors, in a wide range
of ESR values we should implement local
feedback with a compensation network (typeIII).
The typically used compensation network for
voltage-mode controller is shown in figure 15.
In such configuration, the transfer function is
given by:
1
V
+
The error amplifier gain is independent of the
transconductance under the following condition:
By replacing Z
in
and Z
f
according to figure 15, the
transformer function can be expressed as:
-(16)
-
C
L
2
1
75
.
0
F
F
75
F
o
o
z
LC
z
*
*
%
π
=
=
As known, transconductance amplifier has high
impedance (current source) output, therefore,
consideration should be taken when loading the
error amplifier output. It may exceed its
source/sink output current capability, so that the
amplifier will not be able to swing its output
voltage over the necessary range.
The compensation network has three poles and
two zeros and they are expressed as follows:
Cross over frequency is expressed as:
C
C
C
C
R
2
1
F
POLE
4
POLE
4
3
P
+
=
*
*
*
π
2
F
F
For
F
R
*
1
C
1
F
R
1
C
s
P
s
3
4
s
3
POLE
<<
=
*
*
*
π
π
Fig.15: Compensation network with local
feedback and its asymptotic gain plot
IN
m
f
m
o
e
Z
g
1
Z
g
V
=
(
)
[
C
]
)
(
*
+
*
4
C
(
*
)
(
)
(
7
10
3
4
3
4
3
10
8
7
3
3
4
8
C
sR
1
C
C
sR
1
R
R
sC
1
C
sR
1
C
C
sR
1
s
H
+
+
+
+
+
+
=
8
7
10
8
7
2
z
4
3
1
z
3
3
3
4
3
4
3
3
P
7
10
2
P
1
P
R
C
2
1
R
R
C
2
1
F
C
R
2
1
F
C
R
2
1
C
C
C
C
R
2
1
F
C
R
2
1
F
0
F
*
*
)
(
*
*
*
*
*
*
+
*
*
*
π
π
π
π
π
π
+
=
=
=
=
=
o
o
osc
in
7
3
o
C
L
2
1
V
V
C
R
F
*
*
*
*
*
π
=
-(17)
-
1
Z
*
g
and
1
Z
*
g
in
m
f
m
>>
>>
V
O
V
REF
R
9
R
8
R
10
C
7
C
3
C
4
R
3
Ve
F
Z
1
F
Z
2
F
P
2
F
P
3
E/A
Z
f
Z
IN
Frequency
Gain(dB)
H(s) dB
Fb
Comp
16
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