
AD8001
REV. B
–11–
Printed Circuit Board Layout Considerations
As to be expected for a wideband amplifier, PC board parasitics
can affect the overall closed loop performance. Of concern are
stray capacitances at the output and the inverting input nodes. If
a ground plane is to be used on the same side of the board as
the signal traces, a space (5 mm min) should be left around the
signal lines to minimize coupling. Additionally, signal lines con-
necting the feedback and gain resistors should be short enough
so that their associated inductance does not cause high fre-
quency gain errors. Line lengths on the order of less than 5 mm
are recommended. If long runs of coaxial cable are being driven,
dispersion and loss must be considered.
Power Supply Bypassing
Adequate power supply bypassing can be critical when optimiz-
ing the performance of a high frequency circuit. Inductance in
the power supply leads can form resonant circuits that produce
peaking in the amplifier’s response. In addition, if large current
transients must be delivered to the load, then bypass capacitors
(typically greater than 1
μ
F) will be required to provide the best
settling time and lowest distortion. A parallel combination at
least 4.7
μ
F and between 0.1
μ
F and 0.01
μ
F is recommended.
Some brands of electrolytic capacitors will require a small series
damping resistor
≈
4.7
for optimum results
DC E rrors and Noise
T here are three major noise and offset terms to consider in a
current feedback amplifier. For offset errors refer to the equa-
tion below. For noise error the terms are root-sum-squared to
give a net output error. In the circuit below (Figure 43) they are
input offset (V
IO
) which appears at the output multiplied by the
noise gain of the circuit (1 + R
F
/R
I
), Noninverting input current
(I
BN
×
R
N
) also multiplied by the noise gain, and the inverting
input current, which when divided between R
F
and R
I
and sub-
sequently multiplied by the noise gain always appears at the out-
put as I
BN
×
R
F
. T he input voltage noise of the AD8001 is a low
2 nV/
√
Hz
. At low gains though the inverting input current noise
times R
F
is the dominant noise source. Careful layout and de-
vice matching contribute to better offset and drift specifications
for the AD8001 compared to many other current feedback am-
plifiers. T he typical performance curves in conjunction with the
equations below can be used to predict the performance of the
AD8001 in any application.
V
OUT
=
V
IO
×
1
+
R
F
R
I
±
I
BN
×
R
N
×
1
+
R
F
R
I
±
I
BI
×
R
F
R
F
R
I
R
N
I
BN
I
BI
V
OUT
Figure 43. Output Offset Voltage
Driving Capacitive Loads
T he AD8001 was designed primarily to drive nonreactive loads.
If driving loads with a capacitive component is desired, best fre-
quency response is obtained by the addition of a small series re-
sistance as shown in Figure 44. T he accompanying graph shows
the optimum value for R
SERIES
vs. capacitive load. It is worth
noting that the frequency response of the circuit when driving
large capacitive loads will be dominated by the passive roll-off of
R
SERIES
and C
L
.
909
R
SERIES
R
L
500
I
N
C
L
Figure 44. Driving Capacitive Loads
40
0
0
25
30
10
5
20
15
20
10
R
S
C
L
– pF
G = +1
Figure 45. Recommended R
SERIES
vs. Capacitive Load