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參數(shù)資料
| 型號(hào)： | LTC3731CG |
| 廠商： | LINEAR TECHNOLOGY CORP |
| 元件分類： | 穩(wěn)壓器 |
| 英文描述： | 16-Bit Edge-Triggered D-Type Flip-Flop With 3-State Outputs 48-SSOP -40 to 85 |
| 中文描述： | 5 A SWITCHING CONTROLLER, 750 kHz SWITCHING FREQ-MAX, PDSO36 |
| 封裝： | 5.3 MM, PLASTIC, SSOP-36 |
| 文件頁(yè)數(shù)： | 12/16頁(yè) |
| 文件大?。?/td> | 200K |
| 代理商： | LTC3731CG |
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LT3782
12
3782fa
APPLICATIU
For a given V
IN
and V
OUT
, we can calculate the duty cycle
D and then derive the output RMS ripple current from
Figure 6. After choosing output capacitors with sufficient
RMS ripple current rating, we also need to consider the
ESR requirement if Electrolytic caps, Tantulum caps,
POSCAPs or SP CAPs are selected. Given the required
output ripple voltage spec
V
OUT
(in RMS value) and the
calculated RMS ripple current
I
OUT
, one can estimate the
ESR value of the output capacitor to be
W
U
U
ESR
V
I
OUT
OUT
≤
External Regulator to Bias Gate Drivers
If V
IN
is higher than 24V and the applications require the
LT3782 to drive large MOSFETs the IC temperature may
get too high. To reduce heat, an external regulator between
12V to 14V should be used to override the internal V
GBIAS
regulator to supply the current needed for BGATE1 and
BGATE2 (see Figure 7).
1. The supply current into V
IN
. The V
IN
current is the sum
of the DC supply current I
Q
(given in the Electrical
Characteristics) and the MOSFET driver and control
currents. The DC supply current into the V
IN
pin is
typically about 7mA and represents a small power loss
(much less than 1%) that increases with V
IN
. The driver
current results from switching the gate capacitance of
the power MOSFET; this current is typically much larger
than the DC current. Each time the MOSFET is switched
on and then off, a packet of gate charge Q
G
is transferred
from GBIAS to ground. The resulting dQ/dt is a current
that must be supplied to the GBIAS capacitor through
the V
IN
pin by an external supply. In normal operation:
I
Q(TOT)
≈
I
Q
= f Q
G
P
IC
= V
IN
(I
Q
+ f Q
G
)
2. Power MOSFET switching and conduction losses:
P
I
D
R
D
k V
I
D
C
f
FET
O MAX
(
2
MAX
DS ON
(
MAX
T
O
O MAX
(
2
MAX
RSS
=
+
)
)
)
–
–
1
1
2
2
ρ
3. The I
2
R losses in the sense resistor can be calculated
almost by inspection.
P
I
D
R D
R SENSE
(
O MAX
(
2
MAX
MAX
)
)
–
=
1
2
4. The losses in the inductor are simply the DC input
current squared times the winding resistance. Express-
ing this loss as a function of the output current yields:
P
I
D
R
R WINDING
(
O MAX
(
2
MAX
W
)
)
–
=
1
2
Figure 7
3782 F07
2
μ
F
12V
+
GBIAS
GBIAS1
GBIAS2
LT3782
Efficiency Considerations
The efficiency of a switching regulator is equal to the
output power divided by the input power (￥100%). Per-
cent efficiency can be expressed as:
% Efficiency = 100% – (L1 + L2 + L3 + …),
where L1, L2, etc. are the individual loss components as
a percentage of the input power. It is often useful to
analyze individual losses to determine what is limiting the
efficiency and which change would produce the most
improvement. Although all dissipative elements in the
circuit produce losses, four main sources usually account
for the majority of the losses in LT3782 application
circuits:
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