參數(shù)資料
型號(hào)： AD600ARZ
廠商： Analog Devices Inc
文件頁(yè)數(shù)： 14/33頁(yè)
文件大小： 0K
描述： IC AMP VGA DUAL LN 50MA 16SOIC
標(biāo)準(zhǔn)包裝： 1
系列： X-AMP®
放大器類(lèi)型： 可變?cè)鲆?br>
電路數(shù)： 2
轉(zhuǎn)換速率： 275 V/µs
-3db帶寬： 35MHz
電流 - 輸入偏壓： 350nA
電流 - 電源： 11mA
電流 - 輸出 / 通道： 50mA
電壓 - 電源，單路/雙路(±)： ±4.75 V ~ 5.25 V
工作溫度： -40°C ~ 85°C
安裝類(lèi)型： 表面貼裝
封裝/外殼： 16-SOIC（0.295"，7.50mm 寬）
供應(yīng)商設(shè)備封裝： 16-SOIC W
包裝： 管件
產(chǎn)品目錄頁(yè)面： 774 (CN2011-ZH PDF)
AD600/AD602
Rev. F | Page 20 of 32
C1HI
A1CM
A1OP
VPOS
VNEG
A2OP
A2CM
C2HI
C1LO
A1HI
A1LO
GAT1
GAT2
A2LO
A2HI
C2LO
1
2
3
4
5
6
7
14
13
12
11
10
9
8
U2
AD636
VIN
NC
–VS
CAV
dB
BUF OUT
BUF IN
+VS
COM
RL
IOUT
INPUT
1V rms
MAX
(SINE WAVE)
R2 200
R3
133k
U3A
1/2
AD712
R4
3.01k
R5
16.2k
C1
0.1F
C2
2F
NC
Vrms
AF/RF
OUTPUT
C4
4.7F
+6V DEC
R7
56.2k
R6
3.16k
C3
1F
U3B
1/2
AD712
+316.2mV
VOUT
+100mV/dB
0V = 0dB (AT 10mV rms)
NC = NO CONNECT
1
2
3
4
5
6
7
8
16
15
14
13
12
11
10
9
REF
A1
A2
+
–
+
–
U1
AD600
FB
+6V
–6V
+6V
DEC
–6V
DEC
0.1F
POWER SUPPLY
DECOUPLING
NETWORK
CAL
0dB
+6V
DEC
–6V
DEC
–6V
DEC
R1
115
VG
15.625mV/dB
00
53
8-
0
39
450
300
150
10
100
10
1
100m
10m
1m
225
375
350
200
275
425
325
175
250
400
INPUT SIGNAL (V rms)
Figure 41. The Output of This Three-IC Circuit Is Proportional to the Decibel Value of the rms Input
The output of A2 is ac-coupled via another 12 Hz high-pass
filter formed by C2 and the 6.7 kΩ input resistance of the
AD636. The averaging time constant for the rms-dc converter
is determined by C4. The unbuffered output of the AD636 (at
Pin 8) is compared with a fixed voltage of 316 mV set by the
positive supply voltage of 6 V and the R6 and R7 resistors. VREF
is proportional to this voltage, and systems requiring greater
calibration accuracy should replace the supply-dependent
reference with a more stable source.
Any difference in these voltages is integrated by the U3B
op amp, with a time constant of 3 ms formed by the parallel
sum of R6/R7 and C3. If the output of the AD600 is too high,
V rms is greater than the setpoint of 316 mV, causing the output
of U3B—that is, VOUT—to ramp up (note that the integrator is
noninverting). A fraction of VOUT is connected to the inverting
gain-control inputs of the AD600, causing the gain to be
reduced, as required, until V rms is exactly equal to 316 mV, at
which time the ac voltage at the output of A2 is forced to be
exactly 316 mV rms. This fraction is set by R4 and R5 such that
a 15.625 mV change in the control voltages of A1 and A2—
which would change the gain of the cascaded amplifiers by
1 dB—requires a change of 100 mV at VOUT. Note here that,
because A2 is forced to operate at an output level well below its
capacity, waveforms of high crest factor can be tolerated
throughout the amplifier.
To check the operation, assume that an input of 10 mV rms is
applied to the input, which results in a voltage of 3.16 mV rms
at the input to A1, due to the 10 dB loss in the attenuator. If the
system operates as claimed, VOUT (and, hence, VG) should be 0.
This being the case, the gain of both A1 and A2 is 20 dB, and
the output of the AD600 is therefore 100 times (40 dB) greater
than its input, which evaluates to 316 mV rms, the input
required at the AD636 to balance the loop. Finally, note that,
unlike most AGC circuits that need strong temperature
compensation for the internal kT/q scaling, these voltages, and
thus the output of this measurement system, are temperature
stable, arising directly from the fundamental and exact
exponential attenuation of the ladder networks in the AD600.
Typical results are presented for a sine wave input at 100 kHz.
Figure 42 shows that the output is held close to the setpoint of
316 mV rms over an input range in excess of 80 dB.
V
OU
T
(m
V)
00
53
8-
0
40
Figure 42. RMS Output of A2 Held Close to the Setpoint 316 mV
for an Input Range of over 80 dB
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