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| 型號： | AD539KNZ |
| 廠商： | Analog Devices Inc |
| 文件頁數(shù)： | 5/21頁 |
| 文件大?。?/td> | 0K |
| 描述： | IC MULT/DIV DUAL CH LIN 16-DIP |
| 標準包裝： | 1 |
| 功能： | 模擬乘法器/除法器 |
| 位元/級數(shù)： | 雙象限 |
| 封裝/外殼： | 16-DIP（0.300"，7.62mm） |
| 供應商設(shè)備封裝： | 16-PDIP |
| 包裝： | 管件 |
AD539
Rev. B | Page 12 of 20
APPLICATIONS INFORMATION
BASIC MULTIPLIER CONNECTIONS
Figure 20 shows the connections for the standard dual-channel
multiplier, using op amps to provide useful output power and
the AD539 feedback resistors to achieve accurate scaling. The
transfer function for each channel is
VW = VXVY
where the inputs and outputs are expressed in volts (see the
Transfer Function section).
At the nominal full-scale inputs of VX = 3 V and VY = ±2 V, the
full-scale outputs are ±6 V. Depending on the choice of op amp,
their supply voltages may need to be about 2 V more than the
peak output. Thus, supplies of at least ±8 V are required; the
AD539 can share these supplies. Higher outputs are possible if
VX and VY are driven to their peak values of +3.2 V and ±4.2 V,
respectively, when the peak output is ±13.4 V. This requires
operating the op amps at supplies of ±15 V. Under these condi-
tions, it is advisable to reduce the supplies to the AD539 to
±7.5 V to limit its power dissipation; however, with some form
of heat-sinking, it is permissible to operate the AD539 directly
from ±15 V supplies.
09
67
9-
0
2
0
1
2
3
4
16
15
14
13
5
12
6
11
7
10
8
9
AD539
VX
HF COMP
VY1
VY2
+VS
–VS
INPUT
COMMON
OUTPUT
COMMON
NOTES
1. ALL DECOUPLING CAPACITORS ARE 0.47F CERAMIC.
BASE
COMMON
W1
Z1
CHAN1
OUTPUT
CHAN2
OUTPUT
Z2
W2
CC = 3nF
VX
VW1 =
–VXVY1
VW2 =
–VXVY2
NC
CF
+VS
–VS
VY1
VY2
Figure 20. Standard Dual-Channel Multiplier
(16-Lead SBDIP and PDIP Shown)
Viewed as a voltage-controlled amplifier, the decibel gain is simply
G = 20 log VX
where VX is expressed in volts. This results in a gain of 10 dB at
VX = 3.162 V, 0 dB at VX = 1 V, 20 dB at VX = 0.1 V, and so on.
In many ac applications, the output offset voltage (for VX = 0 V
or VY = 0 V) is not a major concern; however, it can be elimi-
nated using the offset nulling method recommended for the
particular op amp, with VX = VY = 0 V.
At small values of VX, the offset voltage of the control channel
degrades the gain/loss accuracy. For example, a ±1 mV offset
uncertainty causes the nominal 40 dB attenuation at VX =
0.01 V to range from 39.2 dB to 40.9 dB. Figure 4 shows the
maximum gain error boundaries based on the guaranteed
control channel offset voltages of ±2 mV for the AD539K and
±4 mV for the AD539J. These curves include all scaling errors
and apply to all configurations using the internal feedback
resistors (W1 and W2 or, alternatively, Z1 and Z2).
Distortion is a function of the signal input level (VY) and the
control input (VX). It is also a function of frequency, although
in practice, the op amp generates most of the distortion at frequen-
cies above 100 kHz. Figure 5 shows typical results at f = 10 kHz
as a function of VX with VY = 0.5 V rms and 1.5 V rms.
In some cases, it may be desirable to alter the scaling. This can
be achieved in several ways. One option is to use both the Z and
W feedback resistors (see Figure 18) in parallel, in which case
VW = VXVY/2. This may be preferable where the output swing
must be held at ±3 V FS (±6.75 peak), for example, to allow the use
of reduced supply voltages for the op amps. Alternatively, the
gain can be doubled by connecting both channels in parallel and
using only a single feedback resistor, in which case VW = 2VXYY
and the full-scale output is ±12 V. Another option is to insert a
resistor in series with the control channel input, permitting the
use of a large (for example, 0 V to 10 V) control voltage. A
disadvantage of this scheme is the need to adjust this resistor to
accommodate the tolerance of the nominal 500 Ω input resistance
at Pin 1, VX. The signal channel inputs can also be resistively
attenuated to permit operation at higher values of VY, in which
case it may often be possible to partially compensate for the
response roll-off of the op amp by adding a capacitor across the
upper arm of this attenuator.
Signal Channel AC and Transient Response
The HF response is dependent almost entirely on the op amp.
Note that the noise gain for the op amp in Figure 20 is determined
by the value of the feedback resistor (6 kΩ) and the 1.25 kΩ
control-bias resistors (see Figure 18). Op amps with provision
for external frequency compensation should be compensated
for a closed-loop gain of 6.
The layout of the circuit components is very important if low
feedthrough and flat response at low values of VX is to be
maintained (see the General Recommendations section).
For wide bandwidth applications requiring an output voltage
swing greater than ±1 V, the LH0032 hybrid op amp is recom-
V; the 3 dB bandwidth exceeds 25 MHz. The effect of signal
feedthrough on the response becomes apparent at VX = 0.01 V.
The minimum feedthrough results when VX is taken slightly
negative to ensure that the residual control channel offset is
exceeded and the dc gain is reliably zero. Measurements show
that the feedthrough can be held to 90 dB relative to full
output at low frequencies and to 60 dB up to 20 MHz with
careful board layout. The corresponding pulse response is
values of VX (3 V and 0.1 V).
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相關(guān)代理商/技術(shù)參數(shù) |
參數(shù)描述 |
|---|---|
| AD539SD | 制造商:Analog Devices 功能描述:Analog Multiplier/Divider 2-Bit 16-Pin SBCDIP 制造商:Rochester Electronics LLC 功能描述:MULTIPLIER IC - Bulk |
| AD539SD/883B | 功能描述:增效器/分頻器 MULTIPLIER IC RoHS:否 制造商:Texas Instruments 產(chǎn)品:Multiplier 邏輯系列: 工作電源電壓: 最大工作溫度:+ 85 C 最小工作溫度:- 40 C 安裝風格:Through Hole 封裝 / 箱體:PDIP-14 |
| AD539SD883B | 制造商:AD 功能描述:* |
| AD539SE/883B | 功能描述:增效器/分頻器 I.C. ANALOG MULTIPLIER IC RoHS:否 制造商:Texas Instruments 產(chǎn)品:Multiplier 邏輯系列: 工作電源電壓: 最大工作溫度:+ 85 C 最小工作溫度:- 40 C 安裝風格:Through Hole 封裝 / 箱體:PDIP-14 |
| AD53ABS | 制造商:POP 功能描述: |
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